Nonlinear signal filtering

ABSTRACT

In a nonlinear signal filtering system, a signal having a series of signal samples is filtered. The signal samples are affected by interactions with adjacent signal samples and nonlinear distortions. The system contains a series of alternating linear system elements and nonlinear system elements that are used for mitigation of distortion resulting from the nonlinear distortions with memory effects. The linear system elements can scale each signal sample in the series of signal samples by scaling parameters and sums a plurality of consecutive scaled signal samples, and the nonlinear system elements can transform the output of the linear system elements according to instantaneous nonlinear functions.

RELATED APPLICATIONS

The application is a continuation of U.S. patent application Ser. No.15/906,958, filed Feb. 27, 2018 and entitled “Nonlinear SignalFiltering”, which claims benefit of U.S. Provisional Patent ApplicationNo. 62/466,513 filed on Mar. 3, 2017 and entitled “Look-Up-Table BasedModification of Transmission Signals”, and claims benefit of U.S.Provisional Patent Application No. 62/527,860 filed on Jun. 30, 2017 andentitled “Nonlinear Signal Filtering,” which are incorporated herein byreference in their entirety for all purposes.

BACKGROUND

Systems affect signals by inducing both linear and nonlineardistortions, including those due to memory effects. Memory in thiscontext means that a system response at a time instant of interest (thatwas otherwise intended to be uncorrelated with other time instances)depends on, and is influenced by, signal values in surrounding timeinstants. Some examples of electrical systems containing signals thatsuffer from linear and nonlinear distortion, including memory effects,include optical communication systems, wireless communication systems,satellite communication systems, computer data storage systems, imageprocessing systems, video processing systems, sound processing systems,and controls systems, among others. The impairments (both linear andnonlinear) diminishing the quality of the useful signal are in practicecommonly countered by some means of filtering, equalization, orcompensation (often used interchangeably).

One method to compensate signals that have linear and nonlineardistortions with memory effects, is accomplished by filters that arebased on polynomial expansions, where the filter output (y[n]) is aweighted linear combination of the input signal (x[n]) at different timeinstances, plus the input signal at different time instances raised to agiven power (determined by the nonlinearity order), plus the (linear)combination of various cross-products of the input signal at differenttime instances each raised to an appropriate power. For example, filterswith the full-complexity polynomial expansion based on the Volterraseries are accordingly called Volterra filters. For example, the outputof a Volterra filter of order 2 and memory of 2 will have the form:

y[3]=c ₁ ·x[1]+c ₂ ·x[2]+c ₃ ·x[3]+c ₁₁ ·x[1]² +c ₂₂ ·x[2]² +c ₃₃ ·x[3]²+c ₁₁ ·x[1]·x[2]+c ₁₃ ·x[1]·x[3]+c ₂₃ ·x[2]·x[3]  (1)

In Equation 1, c_(i) are parameters multiplying the signal at the i^(th)instance in time, c_(jj) are parameters multiplying the squared term ofthe signal at the j^(th) instance in time, and c_(jk) (where j does notequal k) are parameters multiplying the signal cross terms at the j^(th)and k^(th) instances in time. However, filters employing the Volterraseries are complex to implement in practice. Specifically, the number ofparameters in the Volterra approach scales exponentially with the numberof signal instances in surrounding time epochs that affect a givensignal state (i.e., scales exponentially with memory). The exponentialnature of nonlinear filters employing the Volterra series can beexpensive to implement, and impractical in high-speed systems, due tothe large amount of operations that are necessary to be performed, whichin practice correspond to large amounts of RAM, or taps, or excessivepower consumption associated with the number of computations required.Furthermore, filters employing the Volterra series rely on polynomialfunctions, and are not well equipped to mitigate distortions that, inpractice, are not necessarily well approximated by continuouspolynomials. For example, ADC and DAC components often introducenonlinear distortions that are not well approximated by continuouspolynomial functions, and are better approximated by piecewisecontinuous functions. As a result, systems with nonlinear signaldistortions resulting from ADC or DAC components in combination withcomponents that introduce memory effects in the signal are not wellmitigated by filters employing the Volterra series.

Other methods for filtering signals that suffer from both linear andnonlinear distortion are accomplished using polynomial expansionsincluding some, but not all, of the terms of the Volterra series. Onesuch variation of Volterra filters are Memory Polynomial filters, whichcontain a portion of the terms in the Volterra series (e.g., only thediagonal terms) and do not contain the cross-products of the inputsignal at different time instances. For example, the first output (y[1])of a Memory Polynomial filter of order 2 and memory of 3 will have theform:

y[1]=c ₁ ·x[1]+c ₂ ·x[2]+c ₃ ·x[3]+c ₁₁ ·x[1]² +c ₂₂ ·x[2]² +c ₃₃·x[3]²  (2)

In Equation 2, x[n], y[n], and the parameters, c_(i) and c_(jj), aredefined the same as they are in Equation 1. Nevertheless, even thoughmemory polynomials are less complex than Volterra series, the price topay for the omission of the cross-terms is a significant decline inperformance, and they are equally limited to continuous polynomialforms.

Electronic communications systems typically convert a digital inputsignal into an analog form by upconverting, filtering, and amplifyingthe signal for transmission using analog components. The digital andanalog components can achieve only limited accuracy, and nonlineardistortions with memory effects are commonplace. An example ofcomponents that can induce nonlinear distortions, in addition to thedigitizers in communications systems are analog linear power amplifiers.As linear power amplifiers approach the end of their dynamic range,saturation can occur, which induces a departure from a linear behavior,or response, thus, if left unattended, leading to distortions, orotherwise departures from the intended signal shaping. Linear poweramplifiers are some of the more expensive components in transmittersused in communications systems, and less expensive amplifiers tend tohave worse nonlinearity. Additionally, high baud rate digitaltransmission systems tend to suffer from memory effects, which manifestas intersymbol interference (ISI). ISI is exacerbated in systemsutilizing narrow band channels, such as telephone voice communicationchannels, where the channel response to one symbol is not allowed totransgress into the time-slot occupied by the next successive symbol.

High-speed information transmission in fiber-optic communication systemsis another example of a system with linear and nonlinear distortions,including memory effects. In such systems, optical waves are used ascarrier signals, and the information to be transmitted typicallyoriginates in electronic form as digital data. Prior to transmission,the electronic information is imprinted (e.g. modulated) onto an opticalcarrier signal by an optical transmitter. The modulated optical carriersignal is then transmitted over a fiber-optic, and is received by anoptical receiver. Information from the received optical signal is thentransformed back into an electronic form, such as digital data.

Imprinting electronic information onto an optical carrier signal can beperformed by an electro-optical modulator, such as a dual-polarizationMach-Zehnder modulator (DP-MZM). A DP-MZM is capable of modulatinginformation onto each of two orthogonal polarizations of adual-polarized optical carrier signal.

In optical communications systems, as one example, memory effects can becaused by the frequency response of waveguides and electrodes within theDP-MZM in addition to the walk-off effect between the optical andelectrical waves. Thus, impairments such as amplitude loss of the signalat a time t=0 can depend on a signal that was previously transmitted attime t=−1, can additionally depend on a signal transmitted at time t=−2,and so on. This can result in loss, change, or other impairments toinformation even before transmission (e.g., directly at the output ofthe DP-MZM). In addition to the memory effects, the MZM structure (andtherefore, the DP-MZM, too) inherently possesses a nonlinear amplitudecharacteristic.

Another example of a type of optical communications system that can beaffected by linear and nonlinear distortions with memory effects arethose that utilize intensity modulated direct detection (i.e., IMDDsystems). In IMDD systems, the power output of an optical source ismodulated to encode a signal. The optical signal is transmitted througha channel (e.g., through free-space (i.e., air), or through an opticalfiber), and then the signal is then received by a receiver. In an IMDDsystem, the receiver utilizes direct detection, for example by detectingthe signal intensity using a photodiode. Such systems can operate in thewavelength band of visible or infrared light. An additional source ofnonlinear distortions in IMDD systems is related to the fact that thepower of the transmitted signal is related to the square of theintensity of the signal, and it is typically the signal intensity thatis detected (e.g., by a photodiode) rather than the amplitude of theelectric field, often referred to as the ‘square-law’ detection. Thus,the square-law detection acts in IMDD systems acts in addition to anyfurther sources of nonlinearity such as MZIs, driver amplifiers, etc,further complicating detection in these systems.

Another example of a type of optical communications system that can beaffected by linear and nonlinear distortions with memory effects arethose that utilize heterodyning. Such systems encode information in anoptical signal as modulation of the phase and/or frequency (i.e.,wavelength) of electromagnetic radiation. A transmitter can encodeheterodyne modulated information on an optical signal that istransmitted over a channel, and then detected in a receiver. Heterodynedetection in the receiver can employ local oscillators, and the detectedsignal can be compared with the reference light from the localoscillator (LO). Such systems can also operate in the wavelength band ofvisible or infrared light.

Some solutions attempt to reduce, mitigate or eliminate the effects ofnonlinearity in electrical and optical transmission systems.Unfortunately, the presence of nonlinearities within circuitry ofelectrical and optical transmitters can reduce the ability to correctimpairments at the receiver. Such attempted solutions often act onmemoryless nonlinearity, and can thus be incapable of correctingimpairments to the transmission signal that result from system memoryeffects.

Other solutions attempt to correct transmission signal impairments byusing frequency response equalization at the transmitter. However, thesesolutions are often unsatisfactory because, in addition to the frequencyresponse (e.g., the linear response of the system), transmitters oftenpossess a nonlinear nature of the response that is inherent in theamplitude cosine transfer function of the transmitter.

Still other solutions seek to combine linear equalization, as well asequalizing the nonlinear response. However, these solutions areunsatisfactory because they neglect the system memory of the nonlinearresponse of the optical transmitters.

A common solution to correct for memory effects in communication systemsare decision feedback equalizers (DFEs). DFEs typically employ a tappeddelay line, which allows the equalizer to correct a signal sufferingfrom memory effects, such as intersymbol interference. One type of DFEis a time domain DFE (TDDFE), where operations are performed on asymbol-by-symbol basis in the time domain. Several types of DFEs operatein the frequency domain, such as hybrid DFE (HDFE), extensionless HDFE(ELDFE), and iterative block DFE (IBDFE), which can reduce thecomputational complexity by roughly 25% compared with TDDFE. All DFEscan in principle compensate for memory effects in signals withnonlinearity, however, their effectiveness in mitigating nonlinearimpairments is very limited and cannot adequately satisfy therequirements in modern communication, or control systems.

SUMMARY

In some embodiments, a nonlinear signal filtering system is disclosedfor filtering a signal with both memory and nonlinear distortions, wherethe system contains alternating linear system elements and nonlinearsystem elements to compensate for memory effects (i.e., signal states insurrounding time instants affecting a given signal state) and nonlineardistortions.

In some embodiments, a nonlinear signal filtering system is disclosed,comprising a series of one or more filtering stages that filter a signalcomprising a series of signal samples, each filtering stage comprisingalternating linear system elements and nonlinear system elements. Insome embodiments, the linear system elements and nonlinear systemelements correct 1) sample interactions between a plurality ofconsecutive signal samples in the signal, and 2) nonlinear distortionsin a value of each signal sample. In some embodiments, the nonlinearsignal filtering system comprises from 2 to 10 filtering stagesconnected sequentially in series to receive and filter the series ofsignal samples.

In some embodiments, the nonlinear signal filtering system describedabove, filter a signal comprising a first signal sample in the series ofsignal samples affected by an interaction with N consecutive signalsamples adjacent to the first signal sample, and the value of eachsignal sample in the series of signal samples is subject to nonlineardistortions. In some embodiments, the linear system elements in eachfiltering stage comprise linear filtering functions each comprising from1 to N parameters, and the nonlinear system elements in each filteringstage comprise nonlinear filtering functions each comprising from 1 to Mparameters. The total number of parameters used in each filtering stageto correct 1) the sample interactions between the plurality ofconsecutive signal samples in the signal, and 2) the nonlineardistortions in the value of each signal sample, can be equal to, or lessthan the sum of N and M.

In some embodiments, a nonlinear signal filtering system is provided,comprising a first linear system element that receives a signalcomprising a series of signal samples, a first nonlinear system elementconnected to receive an output of the first linear system element, and asecond linear system element connected to receive an output of the firstnonlinear system element. In some embodiments, a first signal sample inthe series of signal samples is affected by an interaction with one ormore consecutive signal samples adjacent to the first signal sample, anda value of each signal sample in the series of signal samples is subjectto nonlinear distortions. In some embodiments, the first linear systemelement scales each signal sample in the series of signal samples byscaling parameters and sums a plurality of consecutive scaled signalsamples, the first nonlinear system element transforms the output of thefirst linear system element according to an instantaneous nonlinearfunction, and the second linear system element scales the output of thefirst nonlinear system element by scaling parameters and sums aplurality of consecutive scaled outputs of the first nonlinear systemelement. In some embodiments, the scaling parameters in the first linearsystem element and the second linear system element and theinstantaneous nonlinear function of the first nonlinear system elementcorrect for the signal sample interactions and the nonlinear distortionsin the value of each signal sample.

In some embodiments, a method is disclosed for filtering a signal withboth memory and nonlinear distortions, where the method includes usingalternating linear system elements, i.e. filters, and nonlinear systemelements to compensate for memory effects (i.e., signal states insurrounding time instants affecting a given signal state) combined withnonlinear distortions, the latter, too possibly having a responsecontaining “memory”.

In some embodiments, one or more systems carry out one or more steps ofa method that involves filtering a nonlinear signal, in which a signalis provided that comprises a series of signal samples, wherein a firstsignal sample in the series of signal samples is affected by aninteraction with one or more consecutive signal samples adjacent to thefirst signal sample, and a value of each signal sample is subject tononlinear distortions. The signal is filtered through a first linearsystem element, wherein the first linear system element scales eachsignal sample by a scaling coefficient and sums a plurality ofconsecutive scaled signal samples. An output of the first linear systemelement is filtered using a first nonlinear system element, wherein thefirst nonlinear system element transforms the output of the first linearsystem element according to an instantaneous nonlinear function. In someembodiments, the scaling parameters in the first linear system elementand the instantaneous nonlinear function of the first nonlinear systemelement can correct for the signal sample interactions and the nonlineardistortions in the value of each signal sample in the signal.

In some embodiments, one or more systems carry out one or more steps ofa method that involves filtering a signal, in which a signal is providedthat comprises a series of signal samples, wherein a first signal samplein the series of signal samples is affected by an interaction with oneor more consecutive signal samples adjacent to the first signal sample,and a value of each signal sample is subject to nonlinear distortions.The signal is filtered through a first linear system element, whereinthe first linear system element scales each signal sample by a scalingcoefficient and sums a plurality of consecutive scaled signal samples.An output of the first linear system element is filtered using a firstnonlinear system element, wherein the first nonlinear system elementtransforms the output of the first linear system element according to amulti-dimensional look-up-table. The scaling parameters in the firstlinear system element and the multi-dimensional look-up-table of thefirst nonlinear system element can correct for the signal sampleinteractions and the nonlinear distortions in the value of each signalsample in the signal.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1A is a simplified schematic diagram of a nonlinear filteringsystem, in accordance with some embodiments.

FIG. 1B is a simplified schematic diagram of a nonlinear filteringsystem, in accordance with some embodiments.

FIG. 1C is a simplified schematic diagram of a nonlinear filteringsystem, in accordance with some embodiments.

FIG. 2A is a plot of a nonlinear distortion that is described by apiece-wise linear function.

FIG. 2B is a plot of a nonlinear distortion that is described by anonlinear polynomial.

FIG. 3 is a flowchart of a method for filtering a nonlinear signal withmemory effects.

FIG. 4 is a flowchart of a method for filtering a nonlinear signal withmemory effects.

FIG. 5A is a simplified schematic of an optical transmitter and idealsignal characteristic graphs.

FIG. 5B is a simplified schematic of an optical transmitter andnon-ideal signal characteristic graphs.

FIG. 5C shows simplified graphs that illustrate a difference betweenideal and non-ideal signal characteristics.

FIGS. 5D and 5E show simplified schematics of a nonlinear filteringsystem in pre-compensation and post-compensation configurations,respectively, in accordance with some embodiments.

FIG. 6A is simplified schematic of a system with input and output plotswithout equalization.

FIG. 6B is a simplified schematic of an equalizer with an output plotwith only linear equalization.

FIG. 6C is a simplified schematic of an equalizer with an output plotwith linear and nonlinear equalization.

FIG. 7A is a simplified schematic of a system in which linear andnonlinear distortions are introduced.

FIG. 7B is a simplified schematic of a nonlinear filtering system(equalizer) in accordance with some embodiments.

FIG. 7C is a simplified schematic of a prior art Volterra or MemoryPolynomial equalizer.

FIG. 8A shows an equalized signal obtained using a prior art Volterraequalizer.

FIG. 8B shows an equalized signal obtained using a prior art MemoryPolynomial equalizer.

FIG. 8C shows an equalized signal obtained using a nonlinear filteringsystem (equalizer) in accordance with some embodiments.

FIG. 9A is a simplified schematic of an example of a MIMO nonlinearequalizer in accordance with some embodiments.

FIG. 9B is a simplified schematic of another example of a MIMO nonlinearequalizer with example functions incorporating nonlinear cross-coupling,in accordance with some embodiments.

FIG. 10 shows a simplified constellation diagram corresponding to amodulated output signal that is unaffected by non-idealities of anoptical transmitter.

FIG. 11A shows a simplified constellation diagram corresponding to amodulated output signal affected by non-idealities of an opticaltransmitter and that is further affected by optical noise.

FIG. 11B shows a simplified constellation diagram corresponding to amodulated output signal affected by non-idealities of an opticaltransmitter, in absence of optical noise.

FIG. 12 shows a simplified constellation diagram corresponding to amodulated output signal of a non-ideal transmitter when equalized by alinear finite impulse response filter and nonlinear equalizer.

FIGS. 13A and 13B are a simplified flowchart of an example process forlook-up-table based modification of transmission signals, in accordancewith some embodiments.

FIG. 14A shows a simplified constellation diagram corresponding to amodulated output signal of a non-ideal transmitter affected bynon-idealities when corrected in accordance with some embodiments.

FIG. 14B shows a simplified constellation diagram corresponding to amodulated output signal of a non-ideal transmitter affected bynon-idealities, in absence of optical noise, when corrected inaccordance with some embodiments.

DETAILED DESCRIPTION

Many electrical system signals are affected by linear distortions,nonlinear distortions, and memory effects. In conventional systems, thecombination of nonlinear distortions and memory distortions have notbeen properly addressed because of the inability to implement filtersthat are capable of compensating for a combination of memory andnonlinear impairments at a level of complexity acceptable for practicalimplementation. A major factor preventing proper distortion reduction insuch systems is the associated complexity of implementing existingsolutions. Described herein is a system for signal filtering to accountfor both linear and nonlinear distortions, including memory effects,using a system that is significantly less complex and/or computationallyexpensive than existing solutions.

The term “memory” in this context means that a system response at a timeinstant of interest (that was otherwise intended to be independent)depends on, and is influenced by, signal states in surrounding timeinstants. One example of a memory distortion is intersymbol interferencein communication systems. It is common for system components to inducelinear and nonlinear distortion. Additionally, some electrical andoptoelectronic components can induce linear or nonlinear effects,including memory, simultaneously.

The filtering systems and methods described herein can be applied to anysignal in a system that suffers from linear distortions and nonlineardistortions, including memory effects. Some examples of systemscontaining such signals that could benefit from the systems and methodsdescribed herein include communication systems (e.g., opticalcommunication systems, wireless communication systems, satellitecommunication systems), computer data storage systems, image processingsystems, video processing systems, sound processing systems, andcontrols systems, among others.

The nonlinear signal filtering systems and methods described herein canbe applied to a signal before the linear and nonlinear distortions andmemory effects occur (i.e., pre-compensation), and/or after the linearand nonlinear distortions and memory effects occur (i.e.,post-compensation). The term “nonlinear signal filtering system” as usedherein, refers to a system capable of correcting a signal suffering fromnonlinear distortions (with or without memory effects). Additionally,the term “filter” or “filtering” can refer to any process (e.g., alinear operation with or without memory, or a nonlinear operation withor without memory) that acts upon and transforms a signal, unlessotherwise specified.

For example, using the systems and methods described herein, high-speedoptical transmission systems, among other types of communicationsystems, can achieve better performance, realize longer reach, andprovide a high degree of reproducibility of information-bearingwaveforms. As a result, improved generation of modulation formats ofhigh cardinality can be achieved, resulting in transmission signalshaving a high density of information packing, and/or high spectralefficiency. Such improvements can be achieved using a system thatcombines the capabilities of linear equalization and nonlineartransmitter equalization and further takes system memory effects intoaccount. Additionally, these improvements can be achieved withoutrequiring significant modifications in existing optical transmissiontechnology or the manufacturing process of the optical transmitters.

A system is disclosed herein for digital filtering of digital timediscretized data representing a signal (e.g. in communication systems asa series of symbols, but more generally as a series of signal samples)impaired by memory, and nonlinear distortions. (The terms “symbol” and“signal sample” are used interchangeably herein, except as explicitlystated in the description or claims.) In some embodiments, the systemcontains a concatenation or series of alternating linear system elements(e.g., elements that perform linear filtering) and nonlinear systemelements (e.g., elements that perform nonlinear transformations). Thelinear filters and nonlinear transformations can compensate for thelinear impairments and linear memory effects (e.g., intersymbolinterference, adjacent consecutive symbol interactions, or signal statesin surrounding adjacent time instants affecting a given signal state),as well as for the nonlinear distortions. The system including linearfilters and nonlinear transformations can also compensate for nonlineardistortions including memory effects, if present. The filtering systemcan be implemented to correct the imperfections or impairments due tothe effects of memory, linear distortion and nonlinear distortion inoptical transmission systems. The term “correct” as used herein, refersto reducing, mitigating or eliminating imperfections affecting thesignal in its generation, or reception, or both, or impairmentsaffecting the signal on the course of its transmission through thechannel. The filtering system can be applied to a signal beforetransmission to pre-compensate for the memory, linear and nonlineareffects in the optical transmission system, or be applied to a signalafter transmission to compensate for the memory, linear and nonlineareffects in the optical transmission system.

In some embodiments, the linear system elements perform linearoperations on a series of symbols (i.e., symbols from an input signal,or symbols that have been transformed by previous system elements) thatare input into the linear system elements, which include operations onmore than one symbol over time. For example, a linear element can be atapped delay line, which convolves an input series of symbols with atemporal impulse response. In contrast, in some embodiments, thenonlinear system elements perform nonlinear operations on a series ofsymbols (i.e., symbols from an input signal, or symbols that have beentransformed by previous system elements) that are input into thenonlinear system elements, which include operations on only one symbol.In other words, in some embodiments, the linear system elements performoperations with memory, while the nonlinear system elements perform onlyinstantaneous operations (i.e., perform operations utilizinginstantaneous functions). The term “instantaneous function”, as usedherein, refers to a function that operates on only one symbol out of aseries of symbols making up a signal. That is in contrast to a functionthat includes memory, and operates on more than one symbol in a seriesof symbols making up a signal (e.g., a function utilized by a tappeddelay line).

An advantage of the systems and methods described herein are that thesystems and methods can be implemented to correct signals with memory,linear impairments and nonlinear distortions without significantlyincreasing the complexity of the system or the number of requiredcomputations. One factor contributing to the low complexity of thesystem is that the number of parameters in the system scales roughlylinearly with the number of signal states or symbols in surrounding timeinstants affecting a given signal state or symbol, rather thanexponentially, as in polynomial filters, such as those employing theVolterra series. Therefore, the systems and methods described herein canbe practical to implement in many electrical systems with signals thatsuffer from both linear and nonlinear distortions, including systemswith memory effects that span over many signal samples (or symbols)within the signal that also have several sources of nonlinearity, suchas high-speed optical transmission systems with higher-order QAM.

The systems and methods described herein, have several key advantagescompared to other systems and methods aimed specifically at correctingdistortions in signals caused by amplifiers with nonlinearcharacteristics. Specifically, the systems and methods described hereinenable the compensation of general nonlinear systems with memory,specifically by means of digital filtering, or by manipulating digitalrepresentation of signals, unlike some prior attempts that are only ableto compensate for distortions in nonlinear systems that can be describedby continuous functions, which, in fact, had no means of implementationin practice. For example, some prior attempts relied on analyticalfunction inverses, which in practice are difficult to determine,rendering those approaches merely theoretical, or conceptual, while theapproach described herein has been demonstrated in practice and on‘real’ data. The systems and methods described herein are able tocompensate for distortions that are described by ad-hoc nonlinearfunctions (i.e., a collection of nonlinear functions, a combinationthereof, piece-wise linear profiles, and piece-wise nonlinearfunctions), which as best as possible mitigate the nonlinear impairment.In some embodiments, the nonlinear functions are instantaneous nonlinearfunctions, as described above. Moreover, the systems and methodsdescribed herein can be implemented in pre-, post- and jointpre-and-post-compensation and/or equalization, i.e., at the transmitter,receiver and partially at both transmitting and the receiving ends ofthe system.

Furthermore, the systems and methods described herein are improvedcompared to previous, superficially similar, attempts in that thesystems and methods described herein are successful in mitigatingsystems incorporating nonlinearity with memory, while relying on asystem and/or method that incorporates only instantaneous (i.e.,memoryless) nonlinear elements and/or steps.

Further yet, the systems and methods described herein unambiguouslypostulate the importance of the sequence of elements (in differentvariants, as dictated by the system under consideration), whereas someprevious attempts aimed at the nonlinear amplifier pre-distortionconsidered an improper ordering of the linear and nonlinear elements forpre-distortion. Additionally, in some embodiments, the present inventionallows doublets or triplets of alternating linear and non-linearelements (e.g., L-NL, NL-L, L-NL-L, or NL-L-NL, where L represents alinear element and NL represents a nonlinear element, as furtherdescribed below).

The nonlinear signal filtering systems and methods described herein canalso be applied to optical communications system that utilize intensitymodulated direct detection (i.e., IMDD systems). The nonlinear filteringsystems can be used to pre-compensate or post-compensate for nonlineardistortions in IMDD systems, which are induced by components in thetransmitter and/or receiver, and/or occurring in the channel duringtransmission. For example, the nonlinear filtering systems cancompensate for the nonlinear relationship between the power modulatedsignal that is transmitted and the signal intensity that is received.

Additionally, the nonlinear signal filtering systems and methodsdescribed herein can also be applied to optical communications systemthat utilize heterodyning. The nonlinear filtering systems can be usedto pre-compensate or post-compensate for nonlinear distortions inheterodyne systems, which are induced by components in the transmitterand/or receiver, and/or occurring in the channel during transmission.

The nonlinear signal filtering systems and methods described herein canalso be applied to signals that are one dimensional, ormultidimensional. For example, a signal carried by electric field(which, as a physical quantity can be described as a complex number, inthe mathematical sense) would have both real and imaginary components(i.e., would correspond to a two-dimensional signal) that suffers fromlinear and nonlinear distortions, with memory effects. This signal canbe filtered using the systems and methods described herein.Additionally, in some embodiments, nonlinear interactions (or coupling)between the dimensions (i.e., interactions between the real andimaginary components in the latter example) of an input signal can alsobe compensated for using the signal filtering systems and methodsdescribed herein.

Systems for Filtering Nonlinear Signals with Memory Effects

In some embodiments, a nonlinear signal filtering system includes aseries of one or more groups of alternating linear and nonlinear systemelements. An example of the linear system element is a linear tappeddelay line (TDL). An example of the nonlinear system element is a filterthat transforms the output of the linear system element by aninstantaneous nonlinear function. These types of linear and nonlinearsystem elements, when concatenated together in series, can compensatefor an interaction with two or more consecutive symbols in the signal(i.e., memory effects), and nonlinear distortions in the amplitude ofthe signal. Furthermore, the implementation of such a system isstraightforward, and does not add significant complexity compared with asystem that can only compensate for linear distortions with memoryeffects, such as a linear feed forward equalizer (FFE), or a decisionfeed-back equalizer (DFE), containing a tapped delay line drivenfeedback loop.

In some embodiments, the nonlinear signal filtering system filters asignal containing a series of symbols, wherein each symbol in the seriesis affected by an interaction with one or more consecutive symbolsadjacent to that symbol (i.e., has system memory effects or symbolinteractions), and the amplitude of each symbol in the series is alsosubject to nonlinear distortions. In some embodiments, the consecutivesymbols are before, or after, or surrounding (before and after) thesymbol under consideration. In some embodiments, the number ofconsecutive symbols that affects the first symbol can be any numberdepending on the system design; however, the number of consecutivesymbols that are accounted for by the linear system elements in thesignal filtering system can be from 1 to 5, or from 2 to 5, or from 1 to10, or from 2 to 10, or from 1 to 20, or from 2 to 20, or from 1 to 100,or from 2 to 100, or from 1 to 200, or from 2 to 200, or from 1 to 2000,or from 2 to 2000. Additionally, in some embodiments, the nonlineardistortions in amplitude are described by functions that are piece-wiselinear, nonlinear functions, or piece-wise nonlinear functions.

In some embodiments, a nonlinear signal filtering system includes afirst linear system element, a first nonlinear system element, and asecond linear system element. In some embodiments, the first linearsystem element convolves the signal with a first impulse response. Inother words, the first linear element scales (i.e., multiplies) eachsymbol in the series by scaling parameters and sums two or moreconsecutive scaled symbols. The term “parameter”, as used herein, refersto a scalar value used by an operation to transform a signal. Forexample, the parameters in the linear system elements can be the scalarcoefficients of the impulse response. In another example, the parametersin a nonlinear system element can be coefficients in a nonlinearfunction, or be scalar values in a look-up-table. In some embodiments,the first nonlinear system element transforms the output of the firstlinear system element according to a nonlinear function, or aninstantaneous nonlinear function. In some embodiments, the second linearsystem element convolves the outputs from the nonlinear element with asecond impulse response. In other words, the second linear systemelement scales each successive output of the first nonlinear element byscaling parameters and sums two or more consecutive scaled symbols. Thenumber of consecutive scaled symbols that are summed by each of thelinear system elements can be from 1 to 5, or from 2 to 5, or from 1 to10, or from 2 to 10, or from 1 to 20, or from 2 to 20, or from 1 to 100,or from 2 to 100, or from 1 to 200, or from 2 to 200, or from 1 to 2000,or from 2 to 2000. The linear system elements can include, but are notlimited to, tapped delay lines.

The nonlinear system element can transform the output of the firstlinear system element by a continuous nonlinear function, or a nonlinearfunction that is piece-wise linear, or a nonlinear polynomial, or apiece-wise nonlinear polynomial. In some embodiments, the nonlinearfunctions are instantaneous nonlinear functions. In some embodiments,the nonlinear function is quadratic, cubic, quartic, higher degree(i.e., 5^(th), 6^(th), 7^(th), or greater than 4^(th) degree),logarithmic, exponential, sinusoidal, inverse-sinusoidal, or sigmoidal.The nonlinear element can also transform the output of the first linearsystem element using a look-up-table (LUT), for example, as described inthe aforementioned U.S. Provisional Patent Application No. 62/466,513.In such cases, the transformation need not be described by an explicitmathematical form. In some embodiments, the scaling parameters in thefirst linear system element and the second linear system element, andthe nonlinear function (or LUT) of the first nonlinear element, arechosen to compensate for the symbol interactions (e.g., memory effects),linear distortions and/or nonlinear distortions in the symbol amplitude.It should be understood that LUTs are not required as nonlinear elementsin the systems described herein. LUTs can be used as the nonlinearelements in some embodiments, and when concatenated in series withlinear system elements with memory (e.g., TDLs), the system cancompensate signals to reduce, mitigate or eliminate nonlineardistortions with memory effects.

One non-limiting example of a nonlinear signal filtering system is shownin FIG. 1A for filtering an input signal 111 to generate an output 114,in accordance with some embodiments. The nonlinear signal filteringsystem 100 shown in the figure includes a first tapped delay line (TDL)(or other linear system element or filter) 101, a nonlinear (NL) systemelement 102, and a second TDL (or other linear system element or filter)103. The input signal 111 generally includes a series of symbols x_(i),where m symbols interact (i.e., induce memory effects) with a givensymbol x_(m), such that the symbols in the signal that interact with asymbol x_(m) is the set:

[x]=x ₁ ,x ₂ ,x ₃ , . . . x _(m-1) ,x _(m).  (3)

In addition to each symbol x_(i) in the series being affected by systemmemory, the amplitude of each symbol x_(i) in the series can also besubject to linear and nonlinear distortions.

The first TDL 101 performs an operation to convolve the input signal 111with an impulse response and generates an output 112 designated w_(i),where

w _(i) =Σa _(i) x _(i) =a ₁ x ₁ +a ₂ x ₂ +a ₃ x ₃ + . . . +a _(m) x_(m).  (4)

As each subsequent symbol x_(i) arrives at the first TDL 101, a newoutput 112 (i.e., w_(i)) is generated according to equation 4. Thefunction governing the operation of the linear system element 101 (i.e.,equation 4) includes a set of parameters a_(i).

The outputs 112 of the first TDL 101 (i.e., w_(i) values) are processedby the nonlinear system element 102. The nonlinear system elements inthis disclosure do not incorporate memory effects, and simply perform anonlinear operation on a given w_(i). For example, the nonlinear systemelement 102 can be a cubic function, and raise each w_(i) to the powerof 3, or other appropriate exponentiation function. Additionally, thenonlinear system element 102 can transform the output 112 (i.e., w_(i))according to a nonlinear function including a set of parameters b_(i).The output 113 of the nonlinear system element 102 is y_(i), and as eachsubsequent output 112 (i.e., w_(i)) arrives at the nonlinear systemelement 102, a new output 113 (i.e., y_(i)) is generated.

Furthermore, the output 113 of the nonlinear system element 102 can betransformed according to the second TDL 103 operating similarly to thefirst TDL 101 to generate the output 114 designated z_(i), where

z _(i) =Σc _(i) y _(i) =c ₁ y ₁ +c ₂ y ₂ +c ₃ y ₃ + . . . +c _(m) y_(m).  (5)

As each subsequent output 113 (i.e., y_(i)) arrives at the second TDL103, a new z_(i) is generated according to equation 5, which includes aset of parameters c_(i). The output 114 of the second TDL 103 istherefore the set of z_(i) symbols.

The parameters of all of the linear and nonlinear system elements of thefilter (i.e., a_(i), b_(i) and c_(i)) can be chosen such that the output114 of the nonlinear signal filtering system 100 is a filtered signal.In some embodiments, the initial input signal 111 has memory effects,and linear and nonlinear distortions; and the effects of the memory,linear and nonlinear distortions in the output filtered signal 114 havebeen reduced, mitigated or eliminated. In some embodiments, the numberof parameters typically needed to accomplish the nonlinear filteringscale approximately linearly with the number of symbols that appreciablyinteract in the memory effects. In this example, the number of each ofthe parameters a_(i) and c_(i) are approximately equal to the number ofsymbols that appreciably interact in the memory effects, and the numberof parameters b_(i) can be a small number (e.g., from 1 to 10).

To further illustrate the operation of the nonlinear signal filteringsystem example depicted in FIG. 1A, consider the simple case where only3 symbols interact in the memory effects, and the nonlinear distortioncan be described by a nonlinear relation. The input signal 111 can thusbe written as x_(i)=(x₁, x₂, x₃). The first TDL 101 operates on theinput signal 111, and the output 112 is described by

w _(i) =Σa _(i) x _(i) =a ₁ x ₁ +a ₂ x ₂ +a ₃ x ₃.  (6)

The nonlinear system element 102 performs a nonlinear operation on theoutput 112, and the output 113 from this element is y_(i). In thisexample, the output 113 is described by a nonlinear relation that is acontinuous nonlinear function, or a nonlinear function that ispiece-wise linear, or a nonlinear polynomial, or a piece-wise nonlinearpolynomial, or a LUT. The output 113 from the nonlinear system element102 will generally contain the cross-terms between different symbolsx_(i) with parameters for each term b_(i), and thereby will incorporatethe nonlinear distortions as well as the memory effects. The output 113from the nonlinear system element 102 is then processed through thesecond TDL 103. The output 114 from the second TDL 103 is described by

z _(i) =Σc _(i) y _(i) =c ₁ y ₁ +c ₂ y ₂ +c ₃ y ₃.  (7)

The output 114 now contains all of the parameters a_(i), b_(i) andc_(i), including terms containing the cross-terms between symbols x_(i).In this example, the number of symbols interacting in the memory is 3,and the nonlinear distortions in the signal are described by a relationincluding parameters b_(i), and therefore the parameters a_(i), b_(i)and c_(i) can be chosen such that the output 114 of the nonlinear signalfiltering system 100 is a filtered signal and the effects of the memoryand nonlinearity in the filtered signal 114 have been reduced, mitigatedor eliminated.

In the previous example, there were 3 symbols interacting. Suppose thatthe nonlinear system element had a second order nonlinear relation withone term (i.e., one b_(i) coefficient was needed to describe therelation). In such a case, the number of parameters needed to filter outthe linear and nonlinear distortions, and memory effects, isapproximately 7 (i.e., three a_(i) parameters, plus one b_(i)coefficient, plus three c_(i) parameters). In the case of the typicalpolynomial filtering (e.g., Volterra filtering) 3 to the power of 2, or9 parameters would need to be defined. In this simple case, theimprovement was therefore relatively modest. However, in a situationwhere 15 symbols are interacting with one another in memory, and thenonlinearity can be described by a third order polynomial, then thenumber of parameters required in a system using typical polynomialfiltering (e.g., Volterra filtering) is approximately 3,375 (i.e.,approximately 15 to the power of 3). Using the systems described above,the number of parameters would be approximately 30 to 40 (i.e., 15 a_(i)parameters, plus fewer than 10 b_(i) parameters, plus 15 c_(i)parameters). Therefore, for systems including memory interactionsbetween subsequent symbols in a signal and nonlinear distortions, thesystems described herein can reduce the number of parameters requiredsignificantly, thereby enabling a practical nonlinear filtering system.Additionally, the systems described herein can operate with a largernumber of symbols, and thereby provide better or more thoroughdistortion correction, than is practical within a Volterra filteringsystem.

The systems and methods described herein correct signals with nonlineardistortions with or without memory using fewer parameters (e.g., simplersystems that require fewer computations) than conventional systems andmethods. In the systems and methods described herein, the number ofparameters required to correct signals with nonlinear distortions withmemory scales roughly linearly with the sum of the number of symbolsinteracting in memory and the degree of the nonlinear functions used.This is in contrast to conventional systems and methods for correctingsignals with nonlinear distortions with or without memory, wherein thenumber of parameters required to correct signals with nonlineardistortions with memory scales roughly exponentially with the number ofsymbols interacting in memory raised to a power roughly equal to thedegree of the nonlinear functions used.

In some embodiments, each stage contains from 1 to 5, or from 1 to 10linear system elements, and from 1 to 5, or from 1 to 10 nonlinearsystem elements, and the linear system elements and nonlinear systemelements within each stage alternate. In some embodiments, the linearsystem elements contain linear filtering functions, and each linearfiltering function has from 1 to N parameters. In some embodiments, thefrom 1 to N parameters, corresponds to the approximate number of symbolsin the signal which interact in memory effects. In some embodiments, thenonlinear system elements contain instantaneous nonlinear filteringfunctions, and each instantaneous nonlinear filtering function has from1 to M parameters. In some embodiments, the from 1 to M parameters,correspond to the approximate degree of the instantaneous nonlinearfiltering function. In some embodiments, the total number of parametersused in each filtering stage to correct 1) the sample interactionsbetween the plurality of consecutive signal samples in the signal, and2) the nonlinear distortions in the value of each signal sample, isequal to, or less than the sum of N and M. In other embodiments, thereare X_(L) linear system elements and X_(NL) nonlinear system element ineach stage, where X_(L) is from 1 to 5, or from 1 to 10, and X_(NL) isfrom 1 to 5, or from 1 to 10. In this case, the total number ofparameters used in each filtering stage to correct a signal, is equalto, or less than the sum of X_(L)*N and X_(NL)*M.

In some embodiments, the nonlinear signal filtering system includesseveral stages, where each stage includes a linear system elementfollowed by a nonlinear system element. In some embodiments, thenonlinear signal filtering system includes from 1 to 10 stages, orincludes 1 stage, or 2 stages, or 3 stages, or 4 stages, or 5 stages, or6 stages, or 7 stages, or 8 stages, or 9 stages, or 10 stages. Thelinear system elements convolve the input to the element with an impulseresponse (i.e., scale each symbol in the series by scaling parametersand sum two or more consecutive scaled symbols). The nonlinear systemelements transform the output of the preceding linear system elementaccording to a nonlinear function. In some cases, an initial linear ornonlinear system element can be included before the first stage. In somecases, a final linear or nonlinear system element can be included afterthe last stage. In some cases, each stage contains a nonlinear systemelement followed by a linear system element. In some cases, each stagecan contain three elements: a first linear system element, followed by anonlinear system element, followed by a second linear system element.Linear filtering system elements in a given stage can include, but arenot limited to, tapped delay lines. Nonlinear filtering system elementscan include elements that transform the output of the linear systemelement in a given stage by a continuous nonlinear function, a nonlinearfunction that is piece-wise linear, a smooth and continuous nonlinearfunction, or a piece-wise nonlinear function. In some cases, thenonlinear function of the nonlinear filtering element is piece-wiselinear and contains many pieces (e.g., greater than 10, or greater than20, or from 3 to 50). The many pieces can be useful to obtain a closefit to a high-order nonlinear function. The nonlinear element can alsotransform the output of the linear system element in a given stage usinga LUT. In such cases, the transformation need not be described by anexplicit mathematical form. In some embodiments, the scaling parametersin the linear system elements, and the nonlinear function (or LUTs) ofthe nonlinear elements, are chosen to compensate for the symbolinteractions (e.g., memory effects) and the nonlinear distortions insymbol amplitude. Each stage in the filtering system adds additionaldegrees of freedom, allowing the filter to compensate for signals thatare affected by symbol interactions (e.g., memory effects) and nonlineardistortions in symbol amplitude requiring many degrees of freedom.

In some embodiments, a nonlinear signal filtering system includes from 1to 10 system stages connected sequentially or concatenated in series.The nonlinear signal filtering system can filter a signal comprising aseries of symbols, where a given symbol in the series is affected by aninteraction with one or more consecutive symbols adjacent to the givensymbol (i.e., memory effects), and the amplitude of each symbol in theseries is subject to nonlinear distortions. The nonlinear signalfiltering system can include a first system stage including a firststage linear system element that scales each symbol in the series byscaling parameters and sums two or more consecutive scaled symbols, anda nonlinear system element that transforms the output of the first stagelinear system element according to a nonlinear function. Then, eachsubsequent system stage can include a linear system element that scalesthe output of the preceding stage by scaling parameters and sums two ormore consecutive scaled symbols, and a nonlinear system element thattransforms the output of the linear system element in the stageaccording to a nonlinear function (or LUT). In some cases, an initiallinear or nonlinear system element can be included before the firststage. In some cases, a final linear or nonlinear system element can beincluded after the last stage. In some cases, each stage contains anonlinear system element followed by a linear system element. In somecases, additional (linear) filtering can be applied at the receiver as astandard part of the signal integrity restoration, to improve thereceived signal quality. In some cases, each stage can contain threeelements: a first linear system element, followed by a nonlinear systemelement, followed by a second linear system element.

The scaling parameters in all of the linear system elements, and thenonlinear functions (or LUTs) of all of the nonlinear elements, can bechosen to compensate for the symbol interactions and the nonlineardistortions in symbol amplitude in the signal.

FIG. 1B shows an example of a nonlinear signal filtering system 150 with4 stages. A signal 161 entering the nonlinear signal filtering system150 contains a series of symbols, wherein a given symbol in the seriesis affected by an interaction with one or more consecutive symbolsadjacent to the given symbol (e.g., has system memory effects), and theamplitude of each symbol in the series is also subject to nonlineardistortions. A first stage 151 contains a linear system element similarto the TDL 101 in FIG. 1A described above, and a nonlinear systemelement similar to element 102 in FIG. 1A described above. Similarly, asecond stage 152, a third stage 153, and a fourth stage 154 each containa linear system element and a nonlinear system element, similar toelements 101 and 102 in FIG. 1A described above. In a multistagenonlinear signal filtering system, such as system 150 in FIG. 1B, theoutput of each stage (e.g., 162, 163, 164 and 165) contains cross-termsincluding more than one symbol in the signal, which allows the system tocompensate for signals with linear and nonlinear distortions, and memoryeffects. The scaling parameters in the linear system elements in eachstage, and the nonlinear functions of the nonlinear elements in eachstage, can be chosen to compensate for the symbol interactions and thenonlinear distortions in symbol amplitude in the signal. As describedabove, an advantage of such a system is that fewer parameters can beused to reduce, mitigate or eliminate the memory and nonlinearitydistortions in the signal.

FIG. 1C shows a nonlimiting example of a nonlinear signal filteringsystem 120 for filtering an input signal 111 to generate an output 114,in accordance with some embodiments. The nonlinear signal filteringsystem 120 shown in the figure includes a first linear system element orfilter (e.g., a TDL) 121, a first nonlinear (NL) system element 122, asecond linear system element or filter (e.g., a TDL) 123, and a secondnonlinear (NL) system element 124. In this example, the linear systemelement 121 convolves the input signal 111 with an impulse function. Theimpulse function is shown in a chart 181, which shows the tap weight onthe vertical axis and the sample number on the horizontal axis. In thisexample, the linear relation described by the chart 181 enables thelinear system element 121 to compensate for approximately 12 symbolsinteracting with a given symbol in memory. The tap weights relate to theparameters used by the linear system element 121. In this example, thenonlinear element 122 uses the relation shown in a chart 182. Theamplitude of the input to the nonlinear system element 122 is shown onthe horizontal axis and the amplitude of the output from the nonlinearsystem element 122 is shown on the vertical axis.

In some embodiments, the parameters used by the linear system elementsand nonlinear systems elements (e.g., a_(i), b_(i), and c_(i) in theexamples above) can be determined using a known input signal withsymbols that are affected by linear and nonlinear distortions, withmemory effects. The affected signal can be processed by the nonlinearsignal filter system, and the parameters used by the linear systemelements and nonlinear systems elements can be varied to minimize theerror between the output of the nonlinear signal filter system and theunaffected known input signal. Various methods of optimization of theparameters, such that the overall distortion is minimized, can be usedin conjunction with the systems described. In some embodiments, theparameters used by the linear system elements and nonlinear systemselements can be determined at system initialization, and/or periodicallythroughout the system operation. In some embodiments, the parametersused by the linear system elements and nonlinear systems elements can bedetermined after a predetermined number of symbols have been filtered.In some embodiments, the parameters used by the linear system elementsand nonlinear systems elements can be determined after the number ofsymbols that has been filtered is greater than 10, or greater than 100,or greater than 1000, or greater than 10⁶, or from 10 to 10⁴, or from 10to 10⁵, or from 10 to 10⁶, or from 10 to 10⁹.

Although the above examples and embodiments describe one dimensionalsignals, the nonlinear signal filtering systems and methods describedabove can also be applied to signals that are multidimensional. The samelinear system elements and nonlinear system elements can be used asdescribed above to compensate linear, nonlinear amplitude distortionsand/or memory effects in multidimensional signals. In some embodiments,the parameters a_(i) used in the linear system elements can also be realor complex, i.e., one dimensional or multidimensional. In compensationof multidimensional signals, the summing done by the linear systemelements can still occur along a single dimension (e.g., when the tapparameters have real, as opposed to imaginary values). One nonlimitingexample of a multidimensional signal is a two-dimensional input signalthat contains real and imaginary parts. In such a case, the linearsystem elements processing that signal can have real and/or complexparameters. For the case where the signal has real and imaginary parts,and the linear system element has complex parameters, the systems andmethods described herein can compensate for signals with linear andnonlinear distortion, including memory effects and/or interactionsbetween the real and imaginary components of a signal.

Some examples of nonlinear distortions are shown in FIGS. 2A and 2B.Some examples of nonlinear distortions are those that occur in thecircuitry of an optical transmitter and receiver in a high-speed opticalcommunication system, as well as in other electrical, radio-frequency(RF), or optoelectrical systems.

FIG. 2A shows an example of a nonlinear amplitude distortion that can bedescribed by a piece-wise linear function. The horizontal axis is theamplitude of the input signal, and the vertical axis is the amplitude ofthe output signal. The dashed line 201 indicates a linear response withno distortion. The solid line 202 shows an example of a saturation(e.g., due to saturation of amplifier components that cannot amplifysignals beyond an available power supply level), where the input signalamplitude is above 0.5 and less than −0.5, the amplitude of the outputis linearly reduced. A nonlinear system element of the present inventioncan compensate for this nonlinearity by multiplying the input signal bya function that is piece-wise linear. The parameters of the piece-wiselinear function can be chosen to compensate the affected signal andreduce, mitigate or eliminate the nonlinear distortion.

FIG. 2B shows an example of a nonlinear amplitude distortion that can bedescribed by a nonlinear polynomial. The horizontal axis is theamplitude of the input signal, and the vertical axis is the amplitude ofthe output signal. The dashed line 203 indicates a linear response withno distortion. The solid line 204 shows an example of a saturation,where the output signal amplitude is the input signal amplitude minus0.3 times the cube of the input signal amplitude, i.e.,A_out=A_in−0.3·(A_in)³. A nonlinear system element of the presentinvention can compensate for this nonlinear distortion by multiplying anaffected input signal by a function that is the inverse of the nonlineardistortion it experienced. Therefore, the parameters of the inversefunction can be chosen to compensate the affected signal and reduce,mitigate or eliminate the nonlinear distortion.

In another example, a nonlinear amplitude distortion can be described bya piece-wise nonlinear polynomial function, where different amplituderanges are described by different linear and/or nonlinear polynomials.

Methods of Filtering Nonlinear Signals with, or Affected by MemoryEffects

A method for filtering a nonlinear signal will now be described. FIG. 3shows an embodiment of a method 300 for filtering a nonlinear signal. Insome embodiments, the method includes receiving (at 301) a signal to befiltered. In some embodiments, the impairments affecting the signal maypossess (or include) memory effects, and linear and/or nonlinearamplitude distortions. At 302, the signal is filtered through a firstTDL, or a first linear system element. At 303, the output of the firstTDL is filtered through a nonlinear filter, or a nonlinear systemelement. At 304, the output of the nonlinear filter is further filteredthrough a second TDL, or a second linear system element.

In some embodiments of the method described above, the signal to befiltered includes a series of symbols, wherein each symbol in the seriesis affected by an interaction with one or more consecutive followingand/or preceding symbols adjacent to that symbol (i.e., memory effectsor, in the case of communication systems, intersymbol interference), andthe amplitude of each symbol in the series is subject to linear andnonlinear distortions. In some embodiments, the signal is then filteredthrough a first linear system element that convolves each symbol with afirst impulse response (i.e., scales each symbol in the series by ascaling coefficient and sums two or more consecutive scaled symbols).The output of the first linear system element is then filtered using afirst nonlinear system element that transforms the output of the firstlinear system element according to a nonlinear function, ortransformation. The nonlinear system element can transform the output ofthe first linear system element by a continuous nonlinear function, or anonlinear function that is piece-wise linear, or a nonlinear polynomial,or a piece-wise nonlinear polynomial, or a piece-wise nonlinearfunction, or using a look-up-table (LUT). The output of the firstnonlinear system element is then filtered using a second linear systemelement that convolves the output of the first nonlinear system elementwith a second impulse response. The scaling parameters in the first andthe second linear system elements, and the nonlinear function of thefirst nonlinear system element, are provided to compensate for thesymbol interactions (i.e., memory effects), the linear distortions andthe nonlinear distortions in symbol amplitude in the signal.

A second method for filtering a nonlinear signal will now be described.FIG. 4 shows an embodiment of a method 400 for filtering a nonlinearsignal. In some embodiments, the method includes receiving (at 401) asignal to be filtered. In some embodiments, the signal includes memoryeffects and linear and/or nonlinear amplitude distortions. At 402, thesignal is filtered through a first stage. The first stage generallyincludes a first stage linear system element and a first stage nonlinearsystem element in series. The signal is first filtered through thelinear system element (e.g., a TDL) in the first stage that scales eachsymbol in the series by a scaling coefficient and sums two or moreconsecutive scaled symbols. The output of the linear system element inthe first stage is then filtered using a nonlinear system element in thefirst stage that transforms the output of the linear system elementaccording to a nonlinear function. At 403, the signal is filteredthrough a series of N additional stages. Each additional stage cancontain an n^(th) stage linear element and an n^(th) stage nonlinearsystem element (where n=1 to N). In each of the N stages, the output ofthe preceding stage (i.e., the (n−1)^(th) stage) is filtered through thelinear system element in the n^(th) stage that scales each symbol in theseries by a scaling coefficient and sums two or more consecutive scaledsymbols. The output of the linear system element in the n^(th) stage isthen filtered using a nonlinear system element in the n^(th) stage thattransforms the output of the linear system element according to anonlinear function. In some cases of this method, an initial linear ornonlinear system element can be included before the first stage, and/ora final linear or nonlinear system element can be included after thelast stage. In some cases of this method, the order of the elements canbe exchanged, and each stage can contain a nonlinear system elementfollowed by a linear system element. In some cases of this method, eachstage can contain three elements: a first linear system element,followed by a nonlinear system element, followed by a second linearsystem element. The scaling parameters in all of the linear systemelements, and the nonlinear functions of all of the nonlinear systemelements, can be provided to compensate for the symbol interactions(i.e., memory effects), the linear distortions, and the nonlineardistortions in symbol amplitude in the signal.

As described above, the linear system elements in the first stage and inthe N additional stages can be a TDL, that convolves each symbol with animpulse response. Also, as described above, the nonlinear systemelements in the first stage and in the N additional stages can transformthe output of the first linear system element by a continuous nonlinearfunction, or a nonlinear function that is piece-wise linear, or anonlinear polynomial, or a piece-wise nonlinear polynomial, or using alook-up-table (LUT).

In some embodiments, the first and/or the second nonlinear signalfiltering method described above can be used to pre-compensate for asignal. In such methods, an input signal can be filtered through thenonlinear signal filtering methods described above before the nonlineardistortions and memory effects occur. Then, the pre-compensated signalcan be transmitted through the system incurring the linear and nonlineardistortions and memory effects before being received. In this case, thelinear and nonlinear distortions and memory effects present in thereceived signal would be reduced, mitigated or eliminated by thepre-compensation.

Alternatively, the first and/or the second nonlinear signal filteringmethod described above can be used to post-compensate a signal. In suchmethods, an input signal can be transmitted through the system incurringlinear and nonlinear distortions and memory effects before beingreceived. Then, at the receiver, the affected signal can be filteredthrough the nonlinear signal filtering methods described above. In thiscase, the linear and nonlinear distortions and memory effects present inthe received signal would be reduced, mitigated or eliminated by thepost-compensation. In some embodiments, the first and/or the secondnonlinear signal filtering method described above can be used to bothpre-compensate and post-compensate a signal.

EXAMPLES Example 1: Compensation of Nonlinear Distortion with Memory inOptical Communication Systems

An example of a system where signals are affected by nonlineardistortions with memory is an optical communication transmission system.FIGS. 5A and 5B show two examples of portions of an opticalcommunication transmission system. FIG. 5A shows a portion of a systemwith components that all have linear responses, while FIG. 5B shows aportion of a system with components that have non-linear responses.

FIG. 5A shows a related art optical transmitter 501 and ideal signalcharacteristic graphs 509 through 511. The optical transmitter 501 ispart of an optical transmission system 500. Some elements are omittedfor ease of illustration and explanation.

As shown, the optical transmitter 501 includes a digital-to-analogconverter (DAC) circuit 502 coupled to amplifier circuits 503 a-d. Theamplifier circuits 503 a-d are coupled to a dual-parallel Mach-Zehndermodulator (DP-MZM) circuit 504. In some embodiments, the amplifiers 503a-d are radio frequency amplifiers.

The DAC circuit 502 receives digital input data 505 and generates analogsignals 506 a-d, which are analog representations of the digital inputdata 505. In some embodiments of this example, the analog signals 506a-d are symbols of a quadrature-amplitude modulation (QAM) scheme, whereeach symbol represents a state of a carrier signal, the state having aspecific phase, amplitude and frequency. In some embodiments of thisexample, a first pair of analog signals, 506 a-b, represent the in-phaseand quadrature components of a first QAM signal, and a second pair ofanalog signals, 506 c-d, can represent the in-phase and quadraturecomponents of a second QAM signal.

The analog signals 506 a-d are received by the amplifier circuits 503a-d which amplify the analog signals 506 a-d to generate amplifiedsignals 507 a-d. The amplified signals 507 a-d are received by theDP-MZM circuit 504, which can imprint (e.g., modulate) the electricalinformation from the amplified signals 507 a-d onto a dual-polarizedoptical carrier signal to generate a modulated optical output signal508. In some embodiments of this example, information from the first QAMsignal (corresponding to the amplified signals 507 a-b) is imprintedonto a first polarization of the dual-polarized optical carrier signal(e.g., the X-polarization), and information from the second QAM signal(corresponding to the amplified signals 507 c-d) is imprinted onto asecond polarization of the dual-polarized optical carrier signal (e.g.,the Y-polarization).

Graphs 509, 510, and 511 have the input signal amplitude on thehorizontal axes, and the output signal amplitude on the vertical axes.Graph 509 of FIG. 5A shows an example analog output signal from the DACcircuit 502 (e.g., the analog signal 506 a-d) based on the digital inputdata 505, and is represented by a digital step function graph. Theanalog output signal shown as a continuous line in graph 509 has anideal quantization characteristic. The output of the DAC circuit ingraph 509 is a quantized (or discretized) transformation of the ideallinear relationship. Graph 510 shows an example amplified output signalfrom an amplifier circuit of the amplifier circuits 503 a-d. Theamplified output signal shown has an ideal linear amplitudecharacteristic. Graph 511 shows an example modulated output signal fromthe DP-MZM circuit 504. The modulated output signal shown has an ideallinear amplitude characteristic.

In contrast to the optical transmitter 501 of FIG. 5A, FIG. 5B shows arelated art optical transmitter 521 and non-ideal signal characteristicgraphs 529 through 531. The optical transmitter 521 is part of anoptical transmission system 520. Some elements are omitted for ease ofillustration and explanation.

As shown, the optical transmitter 521 includes a DAC circuit 522 coupledto amplifier circuits 523 a-d. The amplifier circuits 523 a-d arecoupled to a DP-MZM circuit 524. In some embodiments, the amplifiers 523a-d are radio frequency amplifiers.

The DAC circuit 522 receives digital input data 525 and generates analogsignals 526 a-d, which are analog representations of the digital inputdata 525. The analog signals 526 a-d are received by the amplifiercircuits 523 a-d, which amplify the analog signals 526 a-d to generateamplified signals 527 a-d. The amplified signals 527 a-d are thenreceived by the DP-MZM circuit 524, which imprints information from theamplified signals 527 a-d onto a dual-polarized optical carrier signalto generate a modulated output signal 528. In some embodiments, theanalog signals 526 a-d are symbols of a QAM modulation scheme as wasdiscussed with reference to FIG. 5A.

Due to non-idealities in the DAC circuit 522, the amplifier circuits 523a-d and the DP-MZM circuit 524, information extracted from the modulatedoutput signal 528 may differ significantly from the informationcontained in the digital input data 525. Such non-idealities includenonlinearity, saturation, compression and system memory effects. Graphs529, 530, and 531 have the input signal amplitude on the horizontalaxes, and the output signal amplitude on the vertical axes. In theexample shown in FIG. 5B, graph 529 shows an example analog outputsignal (e.g. the analog output signal 526 a) generated by the DACcircuit 522 based on the digital input data 525, which is represented bya digital step function graph. Graph 530 shows an example amplifiedoutput signal from an amplifier circuit of the amplifier circuits 523a-d. Graph 531 shows an example modulated output signal that is outputfrom the DP-MZM circuit 524.

The differences between signals of the optical transmitter 501 (havingideal signal characteristics) and the optical transmitter 521 (havingnon-ideal and nonlinear signal characteristics) are summarized in FIG.5C. FIG. 5C shows the differences between ideal and non-ideal (“actual”)signal characteristics side-by-side for the graphs in FIGS. 5A and 5B.As shown, the analog output signal 529 has a non-ideal quantization, anda nonlinearly distorted amplitude characteristic, as compared to theideal quantization and undistorted amplitude characteristic of theanalog output signal graph 509. The amplified output signal graph 530shows a reduction in gain due to nonlinearities in the amplifiercircuitry which can cause gain compression and/or saturation, ascompared to the ideal line of the amplitude output signal graph 510. Themodulated output signal graph 531 has a non-ideal sinusoidal amplitudecharacteristic, as compared to the ideal straight line of the modulatedoutput signal graph 511.

In addition to the nonlinear amplitude distortions caused by thecomponents in the optical transmitter system in this example, somecomponents can also cause memory effects. For example, the DP-MZM (e.g.,element 524 in FIG. 5B) can cause memory effects, where a given signalamplitude is affected by one or more symbols surrounding the givensymbol. The DP-MZM 524 is therefore an example of a component that cancause both linear and nonlinear amplitude distortion, and both caninclude memory effects.

In this example, the nonlinear filtering system described above can beused to reduce, mitigate or eliminate the memory and nonlineardistortions in the signal. The nonlinear filtering system can reduce,mitigate or eliminate the memory and nonlinear distortions in the signalbefore transmission through a channel (i.e., in a pre-compensationscheme), or after a signal has been transmitted through the channel andreceived in a receiver (i.e., in a post-compensation scheme). FIG. 5Dshows a simplified schematic of a nonlinear filter pre-compensationscheme in a communication system, and FIG. 5E shows a simplifiedschematic of a nonlinear pre-compensation scheme in a communicationsystem. Referring to FIG. 5D, input data 550 is pre-compensated by anonlinear filter (“precompensator”) 552 as described herein, beforebeing transmitted by a transmitter 554 through a channel 556. The signalis received at a receiver 558, and the memory and nonlinear distortionsin output data 560 have been reduced, mitigated or eliminated at leastpartially as a result of the nonlinear filter of the precompensator 552.Referring to FIG. 5E, on the other hand, input data 570 is transmittedby a transmitter 572 through a channel 574. The signal is received at areceiver 576, and is post-compensated by a nonlinear filter(“postcompensator”) 578 as described herein, such that the memory andnonlinear distortions in output data 580 have been reduced, mitigated oreliminated at least partially as a result of the nonlinear filter of thepostcompensator 578. In some embodiments, both pre-compensation andpost-compensation can be used, for example, by adding a postcompensatorelement (similar to the postcompensator 578 in FIG. 5E) between thereceiver 558 and the output data 560 in FIG. 5D.

In some embodiments, the nonlinear signal filtering system in thisExample includes a first linear system element, a nonlinear systemelement, and a second linear system element (similar to the nonlinearsignal filtering system 100 shown in FIG. 1A, and described throughout).The first linear system element is a TDL that convolves the signal withan impulse response. The nonlinear system element transforms the outputof the first linear system element according to an instantaneousnonlinear function to compensate for the nonlinearity incurred by thesignal. Then, the second linear system element convolves the outputsfrom the nonlinear element with an impulse response. The combination ofthe linear system elements and nonlinear system element allows thisfilter to compensate for both nonlinearities (e.g., caused by the DAC522, the amplifiers 523 a-d and the DP-MZM 524), and memory effects(e.g., caused by the DP-MZM 524), using a system with a relatively smallnumber of parameters describing the relations used by the linear andnonlinear elements.

In this example, it is possible to compensate for the nonlinearamplitude distortions and the memory effects by pre-compensating theinput signal (e.g., the digital input data 525 in FIG. 5B) to accountfor the nonlinear distortions and the memory effects caused in thetransmitter (e.g., 521 in FIG. 5B). It is also possible to compensatefor the nonlinear amplitude distortions and the memory effects bypost-compensating the received signal at the receiver.

Example 2: Nonlinear Signal Compensation

In this example, an input signal is subjected to linear and nonlineardistortion with memory effects, and then compensated to recover theoriginal signal using a nonlinear signal filtering system. FIG. 6A showsa system 600 with an element 602 that induces linear distortion (e.g.,with three-tap memory), an element 603 that causes a nonlineardistortion (e.g., with a cubic polynomial response), a second element604 that induces linear distortion (e.g., with three-tap memory), and anelement 605 that causes a nonlinear distortion (e.g., with a cubicpolynomial response). Elements 602, 603, 604 and 605 also inducedistortions that include memory effects. Plots 611 and 612 of the SignalIn 601 and the System Output without Equalization 610, respectively,have the number of samples (i.e., symbols) of the signal along thehorizontal axes and the amplitude of each symbol in the signal on thevertical axis. The Signal In 601 has 8 levels that are clearlydistinguishable in the plot 611. After passing through the system 600,the System Output 610 has been affected by the nonlinear distortions andlinear distortions, each with memory effects, which manifest as verticalscatter in the plot 612 of the System Output 610 for each symbol.

FIG. 6B shows the System Output 610 processed by an Equalizer 620 toobtain an Equalized Signal 630, as illustrated in plot 631. In thiscase, the Equalizer 620 contains a single linear system element, such asa TDL, capable of convolving the input (i.e., the System Output 610)with an impulse response. The linear system element in the Equalizer 620has a linear response with 11-tap memory that is approximately theinverse of the linear distortion caused by elements 602 and/or 604.After being partially compensated by the Equalizer 620, the EqualizedSignal 630 (plot 631) in this case shows less noise than the SystemOutput 610 (plot 612), but some distortion (i.e., variance in theamplitude) remains in each of the levels.

FIG. 6C shows the System Output 610 processed by an Equalizer 640 toobtain an Equalized Signal 650, as illustrated in plot 651. In thiscase, the Equalizer 640 contains a first linear system element capableof convolving the input with an impulse response (e.g., a first TDL), afirst nonlinear system element, a second linear system element capableof convolving the input with an impulse response (e.g., a second TDL),and a second nonlinear system element. The linear and nonlinear systemelements with memory in the Equalizer 640 have linear and nonlinearresponses with their response functions and parameters chosen tocompensate for the linear and nonlinear distortions with memory effectscaused by the combination of linear and nonlinear distortion elementswith memory 602, 603, 604 and 605, wherein the linear inverse blocksconsist of 11-tap memory filters, and the nonlinear inverse blocksconsist of 5^(th) order polynomials. For example, the linear systemelement can be a TDL with the number of taps needed to account for thenumber of interactions (interaction length) between symbols in thesignal, and the tap weights chosen to offset any linear distortions inthe signal. The response functions of the nonlinear system elements, forexample, can approximate the inverse functions of one or more nonlinearcomponents of the noise in the signal. After being compensated by theEqualizer 640, the Equalized Signal 650 in this case closely resemblesthe System Output 610, as shown in the plot 651.

Example 3: Nonlinear, Volterra and Memory Polynomial Signal Compensation

Similar to Example 2, in this Example an input signal was subjected tolinear and nonlinear distortion with memory effects, and thencompensated to recover the original signal using a nonlinear signalfiltering system. The performance of the nonlinear filtering system(i.e., nonlinear equalizer) described herein was compared toconventional Volterra compensation and Memory Polynomial compensation(i.e., conventional equalizers).

FIG. 7A shows the system that introduced the linear and nonlineardistortions, with the memory effects (elements 702 and 704) onto aninput signal 701 and produced a distorted system output 706.

FIG. 7B illustrates the nonlinear filtering system, described in detailthroughout this disclosure, which contained a nonlinear filteringelement 710 and a linear filtering element 710. The distorted systemoutput 706 was fed into the nonlinear equalizer producing an equalizedsignal 712. In this case, the linear filtering element 710 was a tappeddelay line containing about 10 taps and approximated the inverseoperation of the system element 702 that introduced the lineardistortion with memory. In this case, the nonlinear filtering element708 approximated the inverse operation of the system element 704 thatintroduced the nonlinear distortion with memory. In this case, theinverse operation of the nonlinear distortion was best approximated by apiece-wise continuous function, not a continuous single polynomialacross the amplitude range of interest. Note also that the arrangementsequence of the linear element 710 and the nonlinear element 708 in theequalizer (i.e., linear element 710 is after the nonlinear element 708)is the reverse of the arrangement sequence in the system shown in FIG.7A (i.e., linear element 702 is before the nonlinear element 704).

FIG. 7C shows the Volterra or Memory Polynomial equalizer arrangement.In both cases the distorted system output 706 was fed into theconventional equalizer 714 producing an equalized signal 716. In thisExample, the Volterra equalizer 714 utilized a 5^(th) order Volterraseries with about 30 taps. In this Example, the Memory Polynomialequalizer 714 also utilized a 5^(th) order Volterra series with about 30taps, but only included the diagonal matrix elements and omitted allterms with cross-products.

FIGS. 8A-8C show the equalized signals obtained using each of the threeequalizers. FIG. 8A shows the equalized signal 716 obtained using theconventional Volterra equalizer. Significant noise remained in thesignal which was not mitigated using the conventional Volterraequalizer, and the Q was approximately 14.1 dB. This illustrates thateven though the Volterra series is very effective at mitigating certaintypes of nonlinear distortions with memory, there are types of nonlineardistortions that Volterra is not capable of mitigating, such asdistortions that cannot be well described by a continuous polynomial(e.g., those containing piece-wise continuous functions, or look-uptables).

FIG. 8B shows the equalized signal 716 obtained using the conventionalMemory Polynomial equalizer. Significant noise remained in the signalwhich was not mitigated using the conventional Memory Polynomialequalizer, and the Q in this case was slightly worse than that obtainedusing the full Volterra equalizer, approximately 13 dB. This illustratesagain, that equalization based on the Volterra series can be effectiveat mitigating certain types of nonlinear distortions with memory, butcannot mitigate other types of distortions such as those containingpiece-wise continuous functions that are not able to be well describedby continuous 5^(th) order polynomials.

FIG. 8C shows the equalized signal 712 obtained using the nonlinearequalizer described herein. The distortion reduction was greatlyimproved over both of the conventional equalizers, and the Q in thiscase was greater than 40 dB. This illustrates that equalization based onthe nonlinear equalizer described herein can be effective at mitigatingmany types of nonlinear distortions with memory, including those typesthat cannot be well handled using conventional systems.

Example 4: Multiple-Input Multiple-Output Nonlinear Signal Compensation

In this Example, a nonlinear filtering system (i.e., nonlinearequalizer) similar to that described in Example 2 (FIG. 6C element 640)is capable of processing multiple input signals to produce multipleoutput signals. Such an equalizer can be described as a multiple inputmultiple output (MIMO) equalizer.

FIG. 9A shows an example of a MIMO nonlinear equalizer 900. The multipleinput signals 901 are processed by linear and nonlinear filter elements(902, 903, 904 and 905) to produce the multiple output signals 910. Eachfiltering element 902, 903, 904 and 905 process input signals to produceoutput signals 902 a, 903 a, 904 a and 910, respectively. In thisexample, the linear and nonlinear elements alternate, and a linearfiltering element 902 is connected to a nonlinear filtering element 903,which is connected to a linear filtering element 904, which is connectedto a nonlinear filtering element 905.

The input signals 901, in₁, in₂, . . . in_(N), can each be scalarquantities or vectors. For example, the signals could be vectorscontaining multiple instances of the signal in time and thereforeinclude system memory effects. The intermediate signals 902 a, 903 a,904 a and the output signals 910 can also each be scalar quantities orvectors.

Additionally, the number of input signals to any element can be the sameor different than the number of signals at the output of that element.In other words, the number of signals contained in each of the signals901, 902 a, 903 a and 904 a, and 910 can contain the same number ofsignals or different numbers of signals. In the MIMO systems describedin this Example, the number of signals (e.g., “N” for the input signals901, and/or the output signals 910) can be between 1 and 1000.

FIG. 9B shows another example of a MIMO nonlinear equalizer, in whichthere are 2 input signals 921, and 2 output signals 930. The equalizerincludes alternating linear and nonlinear elements 922, 923, 924 and925.

The linear element 922 in this Example, includes a particularinteraction between the input signals 921 (x_(in) and y_(in)) to theelement 922 and the output signals 944 (x₁ and y₁) from the element 922including cross-coupling between the different input signals (x_(in) andy_(in)). The interaction is shown in inset 940, where differentcomponents of the input signal x_(in) are multiplied by differentparameters h₁₁ and h₁₂, and different components of the input signaly_(in) are multiplied by different parameters h₂₁ and h₂₂. Thedifferently scaled components are then added such that cross-coupling ofthe input signals is included, and the signal component multiplied bycoefficient h₁₁ is added to the component multiplied by coefficient h₂₁to produce output signal x₁, and the signal component multiplied bycoefficient h₁₂ is added to the component multiplied by coefficient h₂₂to produce output signal y₁. Some examples of different components inelectrical and optical systems are the real and imaginary components ofan electrical signal, different polarizations of an optical signal, orthe in-phase and quadrature components of a QAM signal.

In this Example, the nonlinear element 923 includes a particularinteraction between the input signals (x₁ and y₁) to the nonlinearelement 923 and the output signals (x₂ and y₂) from the nonlinearelement 923. In this Example, the nonlinear element 923 operates on theinput signals (x₁ and y₁) using functions f₁ and f₂ to produce theoutput signals (x₂ and y₂). Each of the functions f₁ and f₂ operate onboth input signals x₁ and y₁, thereby incorporating nonlinearcross-coupling between the different input signals. The inset 946 inFIG. 9B shows two example functions for f₁ and f₂, includingcross-coupling between the input signals.

The input signals 921 x_(in) and y_(in) and the output signals 930x_(out) and y_(out) can each be scalar quantities or vectors. Forexample, the signals could be vectors containing multiple instances ofthe signal in time and therefore include system memory effects.

Example 5: Nonlinear Signal Filtering System Including Look-Up-Tables

In this example, an input signal is subjected to linear and nonlineardistortion with memory effects, and then compensated to recover theoriginal signal using a nonlinear signal filtering system including anonlinear system element implemented as, or utilizing, a look-up-table.

Using the systems and methods described in this Example, high-speedoptical transmission systems can achieve better performance, realizelonger reach, and provide a high degree of reproducibility ofinformation bearing waveforms. As a result, improved generation ofmodulation formats of high cardinality can be achieved, resulting intransmission signals having a high density of information packing,and/or high spectral efficiency. Such improvements can be achieved usinga composition that combines the capabilities of linear equalization andnonlinear transmitter equalization and further takes system memoryeffects into account. Additionally, these improvements can be achievedwithout requiring significant modifications in existing opticaltransmission technology and the manufacturing process of the opticaltransmitters.

Additionally, the systems and methods in this Example can be extended tocorrect impairments due to cross-talk between the transmitterpolarizations in the transmitter. In some embodiments, both the linearand nonlinear response of the transmitter are jointly corrected,including the associated linear and nonlinear response and system memoryeffects. Joint correction can occur at both ends of the transmissionsystem (transmission/reception).

In accordance with some embodiments, therefore, systems and methods inthis Example are described for using pre-compensation to reduce,mitigate or eliminate (“correct”) impairments due to nonlinear effectsand system memory effects in optical transmission systems. In someembodiments, pre-compensation can be performed by considering multipletime instances, rather than only a single time instant, therebycharacterizing and correcting for system memory effects of an opticaltransmission system in addition to correcting linear and nonlineareffects.

In some embodiments, the steps of pre-compensation generally includedetermining a multi-level transmitter response of an opticaltransmitter. The multi-level transmitter response can be determined byproviding the optical transmitter with a known multi-level signal. Aknown multi-level signal in this context is a signal that has anamplitude that varies over time. Thus, the transmitter response alsocaptures effects due to system memory. Once determined, the transmitterresponse can be used to pre-emptively modify (e.g. pre-compensate)subsequent signals to correct impairments due to the response of theoptical transmitter.

Pre-compensation can be performed using multi-dimensional look-up-tables(LUTs), wherein a first dimension of each LUT relates to the number ofsignals interacting (i.e., memory) in the nonlinear response, and asecond dimension of each LUT relates to the amplitude of the distortionof the nonlinear response. Memory in this context means that thetransmitter response at one time instant is dependent on the surroundingvalues of the waveform corresponding to other time instants. Themulti-dimensional LUTs can encompass the full span of the transmitterresponse, or they can encompass only a part of the memory. In someembodiments, the multi-dimensional LUTs have a depth (e.g. memory) of 2symbols (e.g. a signal/information state). In other embodiments, theLUTs have a depth of 3 symbols. In still other embodiments, the LUTshave a depth of more than 3 symbols.

By design, or by other practical constraints, the size of the LUT and/orthe complexity of the nonlinearity equalizing circuitry can be chosenwith consideration to system performance (e.g. the ability to closelyreplicate desired waveforms). For example, in an embodiment of adual-polarization optical transmission system that imprints componentsof quadrature-amplitude modulation (QAM) signals onto orthogonalpolarizations of an optical carrier signal, a LUT can be designated foreach quadrature of each QAM signal and for each polarization of theoptical carrier signal.

In some embodiments, LUT entries can be approximated based on a modelfunctional dependence. In some embodiments, LUT entries and laterpre-compensating patterns may be generated based on a polynomialfunction of the sought-after entry in time, as well as the surroundingentries related to the designed waveform.

Because of the described non-idealities of optical transmitters, QAMsymbol information imprinted onto an optical carrier signal by theoptical transmitter (resulting in the modulated output signal) willaccordingly suffer from impairments, as described with respect to FIGS.10-11B. A constellation diagram of a QAM modulation scheme that isun-impaired is discussed next.

FIG. 10 shows a simplified constellation diagram 1000 corresponding to amodulated output signal that is unaffected by non-idealities of theoptical transmitter that generated the modulated output signal. Aconstellation diagram is a two-dimensional scatter plot, in thehorizontal and vertical plane, that represents a signal which has beenmodulated using modulation techniques such as phase-shift keying (PSK)or quadrature-amplitude modulation (QAM). Constellation points of aconstellation diagram are often arranged in a square grid with equalvertical and horizontal spacing. As constellation points become closertogether, the transmission system becomes more susceptible to noise andother impairments.

The simplified constellation diagram 1000 corresponds to a 64-QAMmodulated signal corresponding to a single polarization of adual-polarized optical carrier signal. As shown, the constellationdiagram 1000 is substantially square and evenly-spaced. Thehorizontal-axis of the constellation diagram 1000 corresponds to thein-phase component of the 64-QAM modulated signal (I), and thevertical-axis of the constellation diagram corresponds to the quadraturecomponent (Q) of the 64-QAM modulated signal.

As shown, the in-phase component of a 64-QAM modulated signal includes 8unique amplitude levels that span the horizontal-axis of theconstellation diagram 1000. The quadrature component of a 64-QAMmodulated signal includes 8 unique phase-offsets that span thevertical-axis of the constellation diagram 1000. Thus, 64 unique symbolscan be selected based on a combination of one of the 8 amplitude levelsand one of the 8 phase-offsets.

By way of contrast, FIG. 11A shows a simplified constellation diagram1101 corresponding to a modulated output signal affected bynon-idealities of the optical transmitter that generated the modulatedoutput signal and that is further affected by optical noise. In theexample shown, the simplified constellation diagram 1101 corresponds toa 64-QAM modulated signal that was imprinted onto a dual-polarizedoptical carrier signal. As shown, the information signal is completelylost. This is exemplified by an altogether smeared constellation diagramwithout any discernable (and clearly separated) constellation points.

FIG. 11B shows a simplified constellation diagram 1102 corresponding toa modulated output signal affected by non-idealities of the opticaltransmitter that generated the modulated output signal, in absence ofoptical noise, or any random, stochastic, or non-deterministic effects.As shown, even in absence of optical noise, the effects of transmitternon-idealities on the QAM modulated signal introduce significantsmearing of the constellation diagram.

As discussed previously, a portion of the impairments discussed withreference to FIG. 11A and FIG. 11B can be mitigated using combinedlinear and nonlinear equalization techniques. FIG. 12 shows a simplifiedconstellation diagram 1200 corresponding to a modulated output signalaffected by non-idealities of the optical transmitter that generated themodulated output signal, when equalized by a linear finite impulseresponse (FIR) filter and a nonlinear equalizer. In the example shown,the nonlinear equalizer is implemented as a look-up table (LUT) thatdoes not take system memory into account (e.g., a LUT having a depth ofonly one symbol). As can be seen, practically no improvement of signalquality is made by using the linear FIR filter and the single symbolLUT. In some embodiments, the nonlinear signal filtering system containsa single LUT, and no other linear or nonlinear system elements, and thesingle LUT can pre-, or post-compensate a signal with nonlineardistortions, with or without memory effects. In other embodiments, thenonlinear signal filtering system contains one or more linear systemelements concatenated in series with one or more LUTs, where the LUTsperforms nonlinear transformations (either instantaneous or includingmemory).

As has been described, in some embodiments, pre-compensation isperformed by considering multiple time instances, rather than only asingle time instant, thereby characterizing and correcting for systemmemory effects within an optical transmission system. Opticaltransmitter responses are characterized by providing a known multi-levelsignal to the optical transmitter and characterizing a multi-levelresponse of the transmitter to that known signal.

In this Example, the nonlinear optical transmitter responses with memoryeffects are stored in a look-up-table (LUT) of response representations.In some embodiments, the LUT is multi-dimensional, i.e., multiple inputelements (corresponding to multiple amplitudes at multiple timeinstants) result in multiple transmitter system responserepresentations. Once acquired, transmitter system responserepresentations can be used to pre-compensate subsequent digital data.In some embodiments, a transmitter response representation is acharacterization of the transmitter system response. In someembodiments, a transmitter response representation includes values basedon a characterization of the transmitter system response. In someembodiments, a transmitter response representation includes signalcorrection values based on a characterization of the transmitter systemresponse. In some embodiments, if a particular functional dependence ofthe transmitter response is determined, signal correction values can beapplied without the use of a LUT. In some embodiments, the LUT containssignal correction values instead of transmitter responserepresentations.

The response of the optical transmitter can be determined for the full,or partial, duration of the system memory effects. In some embodiments,the transmitter response may not be performed using a signal that fullypopulates the LUT. Missing LUT entries can be interpolated, orextrapolated between the measured/trained points.

FIGS. 13A-B disclose improvements and modifications to the opticaltransmitter described with reference to FIG. 5B. These improvements andmodifications are also applicable to a broader class of applications inthe electronic and computerized arts including any application thatutilizes a transmitter to transmit information using an electrical,audio, optical or radio signal.

FIG. 13A provides a portion of an example process 1300 for look-up-tablebased modification of transmission signals, in accordance with one ormore example embodiments. The particular steps, order of steps, andcombination of steps are shown for illustrative and explanatory purposesonly. Other embodiments can use other specific steps, orders of steps,and/or combinations of steps to achieve a generally similar result.

At step 1301, a test symbol that is an analog representation of a knowndigital signal is generated at a transmitter (e.g. using thedigital-to-analog converter 522 of the transmitter 521 shown in FIG.5B). The known digital signal can be all, or a portion of, the digitalinput data 525 as was discussed with reference to FIG. 5B and the testsymbol can be a QAM symbol. In some embodiments, the known digitalsignal includes information from an excitation-training waveform.Excitation-training waveforms can include pseudo-random multi-levelsequences (e.g. pseudo-noise sequences). The excitation-trainingwaveform can contain all, or a sub-set, of combinations/permutations oftransmitter output levels (e.g. 8 amplitude levels for a 64-QAM signal)reproducible by the transmitter using the excitation-training waveformfor a desired time window of samples. Given a 64-QAM modulation schemehaving 8 amplitudes (“levels”), each quadrature can be stimulated usingpermutations of M=8 levels. For a multi-level excitation signal used tocharacterize N=3 symbols of system memory, the multi-level sequencewould have at least M^(N)=512 level variations.

At step 1302, a test signal is generated at the transmitter using thetest symbol. In some embodiments, the test signal is a modulated outputsignal generated using a modulator circuit of the transmitter (e.g. theDP-MZM circuit 524 as was discussed with reference to FIG. 5B). Themodulator circuit can imprint information from the test symbol onto anoptical carrier signal to generate the test signal.

Having excited the transmitter system using a known digital signal, thetransmitter response can be determined by comparing a representation ofan ideal output (based on the known digital signal) to a representationof the actual system output.

Accordingly, at step 1303, a test representation that is based on thetest signal is generated. In some embodiments, the test representationis a direct digital representation of the test signal. In otherembodiments, the test representation is a digital representation of thetest signal generated after the test signal is down-converted and/ordemodulated. In still other embodiments, the test representation is ananalog representation of the test signal after the test signal isdown-converted and/or demodulated.

Continuing, at step 1304, a known representation that is based on theknown digital signal is generated. In some embodiments, the knownrepresentation is the known digital signal. In other embodiments, theknown representation is an analog representation of the known digitalsignal.

Then, at step 1305, a transmitter response representation is generatedusing the test representation and the known representation. For example,the known digital signal might correspond to an ideal symbol amplitudeof +3.0 volts. However, due to non-idealities of transmitter circuitryas has been described, the test symbol could have an actual amplitude of+2.7 volts (+0.3 volts lower than ideal). In some embodiments, arepresentation of the ideal amplitude (+3.0 volts) can be compared to arepresentation of the actual amplitude (+2.7 volts) as part ofdetermining the transmitter response representation. In someembodiments, the transmitter response representation includes valuesused to modify or replace the amplitude of a symbol by modifying thedigital value used to generate that symbol, or by modifying theamplitude of the symbol's analog signal directly.

As was previously discussed, to modify digital signals such that theeffects of system memory are mitigated, each transmitter responserepresentation can be stored in the multi-dimensional look-up-table, andretrieved from the look-up-table, taking into account the digital valuesthat came before and/or after the digital value that the transmitterresponse representation is based on.

Accordingly, at step 1306, a look-up-table location (LUT) is determined,the location corresponding to an attribute of the known digital signaland to an attribute of one or more previous known digital signals. Insome embodiments, the LUT location is a multi-dimensional index. In someembodiments, the attribute of the known digital signal is the actualamplitude of the test symbol and/or the test signal corresponding to theknown digital signal. In other embodiments, the attribute of the knowndigital signal is an ideal amplitude of the test symbol and/or the testsignal corresponding to the known digital signal. The attribute of theone or more previous known digital signals can include the amplitude ofthe previous test symbol generated using that previous known digitalsignal and can additionally include the order (e.g. sequentially intime) in which the previous test symbols were generated. Thus, thelocation within the LUT is not only determined using an attribute of aknown digital signal, but is also determined using attributes of otherknown digital signals that surround the known digital signal in time(e.g. were output previously to the known digital signal, or after theknown digital signal). In some embodiments, the LUTs arestored/implemented in one or more storage circuits (e.g. volatile ornon-volatile memory and/or registers) of the optical transmitter. Inother embodiments, LUTs are stored/implemented in one or more storagecircuits coupled to the optical transmitter. Such coupling can includecoupling over a network and the storage circuit can be a server.

At step 1307, the transmitter response representation is stored in thelook-up-table at the determined LUT location. Then, at step 1308, steps1301 through 1307 are repeated using one or more additional knowndigital signals with each of the additional known digital signals usedin place of the known digital signal. Each of the additional transmitterresponse representations depends at least in part on a previous knowndigital signal. The LUT is thus populated with data for each of thevariations of the possible transmitter output levels. In someembodiments, LUT generation is accomplished by sending the known digitalsignal multiple times and averaging, or otherwise weighting thegenerated responses, thus diminishing the effect of noise on the qualityof the LUT entries.

The stored transmitter response representations determined as describedwith reference to FIG. 13A can be used immediately, or at a later time,to modify subsequent digital signals, i.e., digital transmissionsignals, or digital signals that are to be transmitted to a receiver.This is described in FIG. 13B, which provides a portion of the exampleprocess 1300 for look-up-table based modification of transmissionsignals, in accordance with one or more example embodiments.

Based on all or a portion (e.g. a bit sequence) of the digital value ofthe subsequent digital signal to be transmitted, and additionally basedon the digital values of previous subsequent digital signals that havebeen transmitted or future subsequent digital signals to be transmitted,a previously stored transmitter response representation is retrievedfrom the LUT. Accordingly, at step 1309, a LUT location is determinedthat corresponds to attributes of the subsequent digital signal and toone or more previous or future subsequent digital signals. The LUTlocation can be determined using a process similar to that which wasdescribed with reference to step 1306 of FIG. 13A. Then, at step 1310, atransmitter response representation stored at the determined LUTlocation is retrieved from the LUT.

Having retrieved the transmitter response representation, the subsequentdigital signal is modified, at step 1311, using the retrievedtransmitter response representation. In some embodiments, the subsequentdigital signal is modified using a correction value determined using theretrieved transmitter response. In other embodiments, the retrievedtransmitter response includes the correction value. A correction valuecan be used to modify the subsequent digital signal directly, or can beused to correct an analog representation of the subsequent digitalsignal. For example, if the ideal amplitude of the subsequent symbol is+3.0 volts, and the retrieved transmitter response representationindicates that the actual amplitude of the symbol will be reduced by+0.3 volts due to non-idealities of the transmitter, the subsequentsymbol's amplitude can be pre-compensated to have an amplitudecorresponding to +3.3 volts, or other appropriate amplitude that hasbeen determined to result in the desired amplitude for the subsequentsymbol. In some embodiments, after step 1310 and before step 1311 thesignal is further filtered through a linear system element such as a FIRfilter (e.g., a tapped delay line element). In some embodiments, afterstep 1311 and before step 1312 the signal is further filtered through alinear system element such as a FIR filter (e.g., a tapped delay lineelement).

At step 1312, the subsequent symbol is generated (e.g. by a DAC circuitof the transmitter) using the modified subsequent digital signal. Next,at step 1313, a subsequent signal using the subsequent symbol isgenerated at the transmitter (e.g. using a modulator circuit of thetransmitter). The transmitter then transmits the subsequent signal to areceiver at step 1314. The subsequent signal is received by the receiverat step 1315. Then, at step 1316, the receiver generates a receiveddigital representation using the received subsequent signal. Thereceived digital representation substantially matches the subsequentdigital signal due to the modification of the transmitted subsequentsignal.

Example results of pre-compensation as has been described with referenceto FIG. 13A and FIG. 13B are discussed next.

FIG. 14A shows a simplified constellation diagram 1401 corresponding toa modulated output signal of a non-ideal transmitter affected bynon-idealities that has been corrected using look-up-table basedpre-compensation of transmission signals, as described herein. Inaddition to nonlinear equalization using multi-dimensional(multi-symbol) look-up-table based pre-compensation, the transmissionsignal has been equalized using a FIR filter.

FIG. 14B shows a simplified constellation diagram 1402 corresponding toa modulated output signal similar to that which was described withreference to FIG. 14A, in absence of optical noise. In addition tononlinear equalization using look-up-table based pre-compensation, thetransmission signal has been equalized using a FIR filter. As shown inFIG. 14A and in FIG. 14B, a full recovery of the modulated output signalhas been accomplished. Thus, information extracted from the modulatedoutput signal substantially matches information from the correspondingsubsequent digital signal.

Reference has been made in detail to embodiments of the disclosedinvention, one or more examples of which have been illustrated in theaccompanying figures. Each example has been provided by way ofexplanation of the present technology, not as a limitation of thepresent technology. In fact, while the specification has been describedin detail with respect to specific embodiments of the invention, it willbe appreciated that those skilled in the art, upon attaining anunderstanding of the foregoing, may readily conceive of alterations to,variations of, and equivalents to these embodiments. For instance,features illustrated or described as part of one embodiment may be usedwith another embodiment to yield a still further embodiment. Thus, it isintended that the present subject matter covers all such modificationsand variations within the scope of the appended claims and theirequivalents. These and other modifications and variations to the presentinvention may be practiced by those of ordinary skill in the art,without departing from the scope of the present invention, which is moreparticularly set forth in the appended claims. Furthermore, those ofordinary skill in the art will appreciate that the foregoing descriptionis by way of example only, and is not intended to limit the invention.

What is claimed is:
 1. A nonlinear signal filtering system comprising: aseries of one or more filtering stages that filter a signal comprising aseries of signal samples, each filtering stage comprising alternatinglinear system elements and nonlinear system elements; wherein the linearsystem elements and nonlinear system elements correct 1) sampleinteractions between a plurality of consecutive signal samples in thesignal, and 2) nonlinear distortions in a value of each signal sample.2. The nonlinear signal filtering system of claim 1, wherein the linearsystem elements and the nonlinear system elements process multiple inputsignals to produce multiple output signals.
 3. The nonlinear signalfiltering system of claim 1, wherein the linear system elements comprisetapped delay lines.
 4. The nonlinear signal filtering system of claim 1,wherein the signal comprises: a first signal sample in the series ofsignal samples affected by an interaction with N consecutive signalsamples adjacent to the first signal sample; and the value of eachsignal sample in the series of signal samples is subject to nonlineardistortions.
 5. The nonlinear signal filtering system of claim 4,wherein: the linear system elements in each filtering stage compriselinear filtering functions each comprising from 1 to N parameters; thenonlinear system elements in each filtering stage comprise nonlinearfiltering functions each comprising from 1 to M parameters; and thetotal number of parameters used in each filtering stage to correct 1)the sample interactions between the plurality of consecutive signalsamples in the signal, and 2) the nonlinear distortions in the value ofeach signal sample, is equal to, or less than the sum of N and M.
 6. Thenonlinear signal filtering system of claim 5, wherein M is from 1 to 10.7. The nonlinear signal filtering system of claim 5, wherein thenonlinear filtering functions are instantaneous functions selected fromthe group consisting of: piece-wise linear functions, nonlinearfunctions, or piece-wise nonlinear functions.
 8. The nonlinear signalfiltering system of claim 1, comprising from 2 to 10 filtering stagesconnected sequentially in series to receive and filter the series ofsignal samples.
 9. The nonlinear signal filtering system of claim 8,wherein: a first filtering stage comprises a first linear system elementand a first nonlinear system element; each subsequent filtering stagecomprises a subsequent linear system element and a subsequent nonlinearsystem element; the first linear system element in the first filteringstage produces a linear combination of the series of signal samples bymeans of scaling each signal sample in the series of signal samples byfirst scaling parameters, sums a first number of consecutive scaledsignal samples, and produces a first series of linearly transformedsignal samples; the first nonlinear system element in the firstfiltering stage transforms each of the samples in the first series oflinearly transformed signal samples according to a first instantaneousnonlinear function, and produces a first series of nonlinearlytransformed signal samples; the subsequent linear system elements in thesubsequent stages scale each transformed signal sample in the series ofnonlinearly transformed signal samples produced by a preceding stage bysubsequent scaling parameters, sums a subsequent number of consecutivescaled signal samples, and produces a subsequent series of linearlytransformed signal samples; the subsequent nonlinear system elements inthe subsequent stages transform the subsequent series of linearlytransformed signal samples according to a subsequent instantaneousnonlinear function, and produces a subsequent series of nonlinearlytransformed signal samples; and the first scaling parameters, thesubsequent scaling parameters, the first instantaneous nonlinearfunction, and the subsequent instantaneous nonlinear functions correctfor the sample interactions and the nonlinear distortions.
 10. Thenonlinear signal filtering system of claim 8, wherein: each filteringstage comprises one of the linear system elements and one of thenonlinear system elements; a first one of the linear system elements ina first one of the filtering stages receives as its input each signalsample in the series of signal samples; each subsequent linear systemelement receives as its input an output of a preceding nonlinear systemelement; each nonlinear system element receives as its input an outputof a preceding linear system element; each linear system elementproduces an output of linearly transformed signal samples; eachnonlinear system element produces an output of nonlinearly transformedsignal samples; each linear system element scales its input by scalingparameters and sums a plurality of consecutive scaled signal samples foreach linearly transformed signal sample; each nonlinear system elementtransforms its input according to an instantaneous nonlinear functionfor each nonlinearly transformed signal sample.
 11. The nonlinear signalfiltering system of claim 8, wherein: a first filtering stage comprises:a first linear system element that scales each signal sample in theseries of signal samples by scaling parameters and sums a plurality ofconsecutive scaled signal samples; and a first stage nonlinear systemelement that transforms an output of the first linear system elementaccording to an instantaneous nonlinear function; each subsequentfiltering stage comprises: a subsequent linear system element thatscales the output of a preceding stage by scaling parameters and sums aplurality of consecutive scaled signal samples; and a subsequentnonlinear system element, wherein the nonlinear system elementtransforms an output of the preceding linear system element according toan instantaneous nonlinear function; and the scaling parameters in thelinear system elements and the instantaneous nonlinear functions of thenonlinear system elements correct for the sample interactions and thenonlinear distortions in the value of each signal sample.
 12. Thenonlinear signal filtering system of claim 8, wherein: a first filteringstage comprises a first linear system element and a first nonlinearsystem element; a second filtering stage comprises a second linearsystem element and a second nonlinear system element; the first linearsystem element scales each signal sample in the series of signal samplesby first scaling parameters, sums a first number of consecutive scaledsignal samples, and produces a first series of linearly transformedsignal samples; the first nonlinear system element transforms the firstseries of linearly transformed signal samples according to a firstinstantaneous nonlinear function, and produces a first series ofnonlinearly transformed signal samples; the second linear system elementscales each transformed signal sample in the first series of nonlinearlytransformed signal samples by second scaling parameters, sums a secondnumber of consecutive scaled signal samples, and produces a secondseries of linearly transformed signal samples; the second nonlinearsystem element transforms the second series of linearly transformedsignal samples according to a second instantaneous nonlinear function,and produces a second series of nonlinearly transformed signal samples;and the first and second scaling parameters and the first and secondinstantaneous nonlinear functions correct for the sample interactionsand the nonlinear distortions.
 13. A nonlinear signal filtering systemcomprising: a first linear system element that receives a signalcomprising a series of signal samples; a first nonlinear system elementconnected to receive an output of the first linear system element; and asecond linear system element connected to receive an output of the firstnonlinear system element; and wherein: a first signal sample in theseries of signal samples is affected by an interaction with one or moreconsecutive signal samples adjacent to the first signal sample; a valueof each signal sample in the series of signal samples is subject tononlinear distortions; the first linear system element scales eachsignal sample in the series of signal samples using scaling parametersand sums a plurality of consecutive scaled signal samples; the firstnonlinear system element transforms the output of the first linearsystem element according to an instantaneous nonlinear function; thesecond linear system element scales the output of the first nonlinearsystem element by scaling parameters and sums a plurality of consecutivescaled outputs of the first nonlinear system element; and the scalingparameters in the first linear system element and the second linearsystem element and the instantaneous nonlinear function of the firstnonlinear system element correct for the signal sample interactions andthe nonlinear distortions in the value of each signal sample.
 14. Thenonlinear signal filtering system of claim 13, wherein the consecutivesignal samples are one of: before the first signal sample, after thefirst signal sample, or both before and after the first signal sample;and the number of consecutive scaled signal samples that are summed bythe first linear system element is from 1 to
 200. 15. The nonlinearsignal filtering system of claim 13, wherein the nonlinear distortionsin the value of each signal sample are described by functions selectedfrom the group consisting of: piece-wise linear functions, nonlinearfunctions, or piece-wise nonlinear functions.
 16. The nonlinear signalfiltering system of claim 13, wherein the first linear system element isa tapped delay line.
 17. The nonlinear signal filtering system of claim13, wherein the instantaneous nonlinear function of the first nonlinearsystem element is a function selected from the group consisting of:piece-wise linear functions, nonlinear functions, or piece-wisenonlinear functions.
 18. The nonlinear signal filtering system of claim13, wherein the second linear system element is a tapped delay line. 19.A method for filtering a signal comprising: providing a signalcomprising a series of signal samples, wherein a first signal sample inthe series of signal samples is affected by an interaction with one ormore consecutive signal samples adjacent to the first signal sample, anda value of each signal sample is subject to nonlinear distortions;filtering the signal through a first linear system element, wherein thefirst linear system element scales each signal sample by a scalingparameter and sums a plurality of consecutive scaled signal samples; andfiltering an output of the first linear system element using a firstnonlinear system element, wherein the first nonlinear system elementtransforms the output of the first linear system element according to aninstantaneous nonlinear function; wherein the scaling parameters in thefirst linear system element and the instantaneous nonlinear function ofthe first nonlinear system element correct for the signal sampleinteractions and the nonlinear distortions in the value of each signalsample in the signal.
 20. The method of claim 19, wherein theconsecutive signal samples are selected from the group consisting of: aset of signal samples before the first signal sample, a set of signalsamples after the first signal sample, or a set of signal samples bothbefore and after the first signal sample, and the number of consecutivescaled signal samples that are summed by the first linear system elementis from 1 to 200.